Pulse compression is a signal processing technique commonly used by radar, sonar and echography to increase the range resolution as well as the signal to noise ratio. This is achieved by modulating the transmitted pulse and then correlating the received signal with the transmitted pulse.
The simplest signal a pulse radar can transmit is a sinusoidal-amplitude pulse, and carrier frequency, , truncated by a rectangular function of width, . The pulse is transmitted periodically, but that is not the main topic of this article; we will consider only a single pulse, . If we assume the pulse to start at time , the signal can be written the following way, using the complex notation:
Let us determine the range resolution which can be obtained with such a signal. The return signal, written , is an attenuated and time-shifted copy of the original transmitted signal (in reality, Doppler effect can play a role too, but this is not important here.) There is also noise in the incoming signal, both on the imaginary and the real channel, which we will assume to be white and Gaussian (this generally holds in reality); we write to denote that noise. To detect the incoming signal, matched filtering is commonly used. This method is optimal when a known signal is to be detected among additive white Gaussian noise.
In other words, the cross-correlation of the received signal with the transmitted signal is computed. This is achieved by convolving the incoming signal with a conjugated and time-reversed version of the transmitted signal. This operation can be done either in software or with hardware. We write for this cross-correlation. We have:
If the reflected signal comes back to the receiver at time and is attenuated by factor , this yields:
Since we know the transmitted signal, we obtain:
where , is the result of the intercorrelation between the noise and the transmitted signal. Function is the triangle function, its value is 0 on , it increases linearly on where it reaches its maximum 1, and it decreases linearly on until it reaches 0 again. Figures at the end of this paragraph show the shape of the intercorrelation for a sample signal (in red), in this case a real truncated sine, of duration seconds, of unit amplitude, and frequency hertz. Two echoes (in blue) come back with delays of 3 and 5 seconds and amplitudes equal to 0.5 and 0.3 times the amplitude of the transmitted pulse, respectively; these are just random values for the sake of the example. Since the signal is real, the intercorrelation is weighted by an additional 1⁄2 factor.
If two pulses come back (nearly) at the same time, the intercorrelation is equal to the sum of the intercorrelations of the two elementary signals. To distinguish one "triangular" envelope from that of the other pulse, it is clearly visible that the times of arrival of the two pulses must be separated by at least so that the maxima of both pulses can be separated. If this condition is not met, both triangles will be mixed together and impossible to separate.
Since the distance travelled by a wave during is (where c is the speed of the wave in the medium), and since this distance corresponds to a round-trip time, we get:
|The range resolution with a sinusoidal pulse is where is the pulse Duration and, , the speed of the wave.
Conclusion: to increase the resolution, the pulse length must be reduced.
|Before matched filtering||After matched filtering|
The instantaneous power of the transmitted pulse is . The energy put into that signal is:
Similarly, the energy in the received pulse is . If is the standard deviation of the noise, the signal-to-noise ratio (SNR) at the receiver is:
The SNR is proportional to pulse duration , if other parameters are held constant. This introduces a tradeoff: increasing improves the SNR, but reduces the resolution, and vice versa.
How can one have a large enough pulse (to still have a good SNR at the receiver) without poor resolution? This is where pulse compression enters the picture. The basic principle is the following:
In radar or sonar applications, linear chirps are the most typically used signals to achieve pulse compression. The pulse being of finite length, the amplitude is a rectangle function. If the transmitted signal has a duration , begins at and linearly sweeps the frequency band centered on carrier , it can be written:
The chirp definition above means that the phase of the chirped signal (that is, the argument of the complex exponential), is the quadratic:
thus the instantaneous frequency is (by definition):
which is the intended linear ramp going from at to at .
The relation of phase to frequency is often used in the other direction, starting with the desired and writing the chirp phase via the integration of frequency:
As for the "simple" pulse, let us compute the cross-correlation between the transmitted and the received signal. To simplify things, we shall consider that the chirp is not written as it is given above, but in this alternate form (the final result will be the same):
Since this cross-correlation is equal (save for the attenuation factor), to the autocorrelation function of , this is what we consider:
It can be shown that the autocorrelation function of is:
The maximum of the autocorrelation function of is reached at 0. Around 0, this function behaves as the sinc (or cardinal sine) term, defined here as . The −3 dB temporal width of that cardinal sine is more or less equal to . Everything happens as if, after matched filtering, we had the resolution that would have been reached with a simple pulse of duration . For the common values of , is smaller than , hence the pulse compression name.
Since the cardinal sine can have annoying sidelobes, a common practice is to filter the result by a window (Hamming, Hann, etc.). In practice, this can be done at the same time as the adapted filtering by multiplying the reference chirp with the filter. The result will be a signal with a slightly lower maximum amplitude, but the sidelobes will be filtered out, which is more important.
|The distance resolution reachable with a linear frequency modulation of a pulse on a bandwidth is: where is the speed of the wave.|
|Ratio is the pulse compression ratio. It is generally greater than 1 (usually, its value is 20 to 30).|
The energy of the signal does not vary during pulse compression. However, it is now located in the main lobe of the cardinal sine, whose width is approximately . If is the power of the signal before compression, and the power of the signal after compression, we have:
As a consequence:
|After pulse compression, the power of the received signal can be considered as being amplified by . This additional gain can be injected in the radar equation.|
While pulse compression can ensure good SNR and fine range resolution in the same time, digital signal processing in such a system can be difficult to implement because of the high instantaneous bandwidth of the waveform ( can be hundreds of megahertz or even exceed 1 GHz.) Stretch Processing is a technique for matched filtering of wideband chirping waveform and is suitable for applications seeking very fine range resolution over relatively short range intervals.
Picture above shows the scenario for analyzing stretch processing. The central reference point(CRP) is in the middle of the range window of interest at range of , corresponding to a time delay of .
If the transmitted waveform is the chirp waveform:
then the echo from the target at distance can be expressed as:
where is proportional to the scatterer reflectivity. We then multiply the echo by and the echo will become:
where is the wavelength of electromagnetic wave in air.
After conducting sampling and discrete Fourier transform on y(t) the sinusoid frequency can be solved:
and the differential range can be obtained:
To show that the bandwidth of y(t) is less than the original signal bandwidth , we suppose that the range window is long. If the target is at the lower bound of the range window, the echo will arrive seconds after transmission; similarly, If the target is at the upper bound of the range window, the echo will arrive seconds after transmission. The differential arrive time for each case is and , respectively.
We can then obtain the bandwidth by considering the difference in sinusoid frequency for targets at the lower and upper bound of the range window:
|Through stretch processing, the bandwidth at the receiver output is less than the original signal bandwidth if , thereby facilitating the implementation of DSP system in a linear-frequency-modulation radar system.|
To demonstrate that stretch processing preserves range resolution, we need to understand that y(t) is actually an impulse train with pulse duration T and period , which is equal to the period of the transmitted impulse train. As a result, the Fourier transform of y(t) is actually a sinc function with Rayleigh resolution . That is, the processor will be able to resolve scatterers whose are at least apart.
which is the same as the resolution of the original linear frequency modulation waveform.
Although stretch processing can reduce the bandwidth of received baseband signal, all of the analog components in RF front-end circuitry still must be able to support an instantaneous bandwidth of . In addition, the effective wavelength of the electromagnetic wave changes during the frequency sweep of a chirp signal, and therefore the antenna look direction will be inevitably changed in a Phased array system.
Stepped-frequency waveforms are an alternative technique that can preserve fine range resolution and SNR of the received signal without large instantaneous bandwidth. Unlike the chirping waveform, which sweeps linearly across a total bandwidth of in a single pulse, stepped-frequency waveform employs an impulse train where the frequency of each pulse is increased by from the preceding pulse. The baseband signal can be expressed as:
where is a rectangular impulse of length and M is the number of pulses in a single pulse train. The total bandwidth of the waveform is still equal to , but the analog components can be reset to support the frequency of the following pulse during the time between pulses. As a result, the problem mentioned above can be avoided.
To calculate the distance of the target corresponding to a delay , individual pulses are processed through the simple pulse matched filter:
and the output of the matched filter is:
If we sample at , we can get:
where l means the range bin l. Conduct DTFT (m is served as time here) and we can get:
,and the peak of the summation occurs when .
Consequently, the DTFT of provides a measure of the delay of the target relative to the range bin delay :
where c is the speed of light.
To demonstrate stepped-frequency waveform preserves range resolution, it should be noticed that is a sinc-like function, and therefore it has a Rayleigh resolution of . As a result:
and therefore the differential range resolution is :
which is the same of the resolution of the original linear-frequency-modulation waveform.
There are other means to modulate the signal. Phase modulation is a commonly used technique; in this case, the pulse is divided in time slots of duration for which the phase at the origin is chosen according to a pre-established convention. For instance, it is possible to not change the phase for some time slots (which comes down to just leaving the signal as it is, in those slots) and de-phase the signal in the other slots by (which is equivalent of changing the sign of the signal). The precise way of choosing the sequence of phases is done according to a technique known as Barker codes. It is possible to code the sequence on more than two phases (polyphase coding). As with a linear chirp, pulse compression is achieved through intercorrelation.
The advantages of the Barker codes are their simplicity (as indicated above, a de-phasing is a simple sign change), but the pulse compression ratio is lower than in the chirp case and the compression is very sensitive to frequency changes due to the Doppler effect if that change is larger than .